Qualifying available reverse link coding rates from access channel power setting

ABSTRACT

Methods and apparatuses are disclosed regarding a wireless field unit, which may receive a plurality of forward link assignment messages for a plurality of time slots for a plurality of forward link transmissions, each message including an indication of a modulation and a code rate associated with a respective forward link transmission. The field unit may receive at least one of the forward link transmissions in at least one time slot at the respective indicated modulation and code rate. The field unit may receive a plurality of reverse link assignment messages for a plurality of time slots for a plurality of reverse link transmissions, each message including an indication of a modulation and a code rate associated with a respective reverse link transmission. The field unit may transmit at least one of the reverse link transmissions in at least one time slot at the respective indicated modulation and code rate.

CROSS REFERENCE TO RELATED APPLICATIONS

This application is a continuation of U.S. patent application Ser. No.15/350,990 filed Nov. 14, 2016, which is a continuation of U.S. patentapplication Ser. No. 14/935,677 filed Nov. 9, 2015, which issued as U.S.Pat. No. 9,497,761 on Nov. 15, 2016, which is a continuation of U.S.patent application Ser. No. 14/462,124 filed Aug. 18, 2014, which issuedas U.S. Pat. No. 9,185,604 on Nov. 10, 2015, which is a continuation ofU.S. patent application Ser. No. 11/295,270 filed Dec. 6, 2005, whichissued as U.S. Pat. No. 8,811,367 on Aug. 19, 2014, which is acontinuation of U.S. patent application Ser. No. 09/792,637 filed Feb.23, 2001, which issued as U.S. Pat. No. 7,006,483 on Feb. 28, 2006, thecontents of which are hereby incorporated by reference herein.

BACKGROUND OF THE INVENTION

The first generation of personal wireless communication devices, such ascellular radio telephones, operated by allocating distinct individualradio carrier frequencies to each user. For example, in an AdvancedMobile Phone Service (AMPS) type cellular mobile telephone, two 30kiloHertz (kHz) bandwidth channels are allocated to support full duplexaudio communication between each subscriber unit and a base station. Thesignals within each such channel are modulated using analog techniquessuch as Frequency Modulation (FM).

Later generation systems make use of digital modulation techniques inorder to allow multiple users to access the same frequency spectrum atthe same time. These techniques ostensibly increase system capacity fora given available radio bandwidth. The technique which has emerged asthe most popular within the United States is a type of Code DivisionMultiple Access (CDMA). With CDMA, each traffic signal is first encodedwith the pseudorandom (PN) code sequence at the transmitter. Thereceivers include equipment to perform a PN decoding function in such away that signals encoded with different PN code sequences or withdifferent code phases can be separated from one another. Because PNcodes in and of themselves do not provide perfect separation of thechannels, certain systems have an additional layer of coding referred toas “orthogonal codes” in order to reduce interference between channels.

In order for the PN and orthogonal code properties to operate properlyat a receiver, certain other design considerations must be taken intoaccount. For signals traveling in a reverse link direction, that is,from a mobile unit back to a central base station, power levels must becarefully controlled. In particular, the orthogonal properties of thecodes are optimized for the situation where individual signals arrive atthe receiver with approximately the same power level. If they do not,channel interference increases. It has been possible in the past to setpower levels individually to optimize each channel, by for example,adjusting it to affect an optimum received power level at the basestation.

Newer generation systems also make use of coding algorithms such asforward error correction (FEC) type algorithms based upon convolutional,Reed-Solomon, or other types of codes. Such FEC codes can be used toincrease effective signal-to-noise ratio at the receiver. While suchcodes do provide increased performance in terms of lower bit error ratesin noisy environments, by themselves they do not improve thedifficulties associated with co-channel interference. Furthermore, theintroduction of the possibility that a given field unit might be using adifferent FEC coding rate than another unit exacerbates design decisionswith respect to prudent power management from the perspective of thesystem as a whole.

SUMMARY OF THE INVENTION

Methods and apparatuses are disclosed regarding a wireless field unit,which may receive a plurality of forward link assignment messages for aplurality of time slots for a plurality of forward link transmissions,each message including an indication of a modulation and a code rateassociated with a respective forward link transmission. The wirelessfield unit may receive at least one of the forward link transmissions inat least one time slot at the respective indicated modulation and coderate. The wireless field unit may receive a plurality of reverse linkassignment messages for a plurality of time slots for a plurality ofreverse link transmissions, each message including an indication of amodulation and a code rate associated with a respective reverse linktransmission. The wireless field unit may transmit at least one of thereverse link transmissions in at least one time slot at the respectiveindicated modulation and code rate.

The wireless field unit may also transmit an indication of an amount ofexcess power that the field unit is capable of using. In response to thetransmitted indication of the amount of excess power, the field unit mayreceive a reverse link assignment message. In addition, the wirelessfield unit may receive power setting information for a first reverselink channel and a second reverse link channel. Further, the firstreverse link channel may be assigned in response to at least onereceived reverse link assignment message.

Methods and apparatuses are disclosed regarding a wireless field unit,which may receive a plurality of forward link assignment messages forthe wireless field unit over at least one first code channel. Each ofthe forward link assignment messages may indicate a modulation type, adata rate and assigned channel codes for a respective assigned forwardlink transmission. Also, forward link transmissions may be timemultiplexed between wireless field units. The wireless field unit mayreceive a plurality of assigned forward link transmissions. In addition,the wireless field unit my process each of the received assigned forwardlink transmissions in response to the respective received forward linkassignment messages. Further, the wireless field unit may receive powercontrol information in assigned time intervals on a time divisionmultiplexed second code channel, wherein the time division multiplexedsecond code channel is time multiplexed between a plurality of wirelessfield units

Methods and apparatuses are disclosed regarding data rate and resourceallocation decisions which are made for a communications channel, suchas a wireless reverse connection. The wireless reverse connection may bebetween stations. One of the stations may be a base station and anotherstation may be a field unit. The field unit may receive a plurality offorward link assignment messages for a plurality of time slots for aplurality of forward link transmissions. Each forward link assignmentmessage may include an indication of a modulation and a code rateassociated with a respective forward link transmission. Also, the fieldunit may receive at least one of the forward link transmissions in atleast two of the time slots, and each received forward link transmissionmay be received at the respective indicated modulation and code rate.Further, the field unit may receive a plurality of reverse linkassignment messages for a plurality of time slots for a plurality ofreverse link transmissions. Each reverse link assignment message mayinclude an indication of a modulation and a code rate associated with arespective reverse link transmission. In addition, the field unit maytransmit at least one of the reverse link transmissions in at least twoof the time slots and each transmitted reverse link transmission may betransmitted at the respective indicated modulation and code rate. In anexample, the field unit may transmit an indication of an amount ofexcess power that the field unit is capable of using. In response to thetransmitted indication of the amount of excess power, the field unit mayreceive a reverse link assignment message.

The present invention is a feature of a wireless data communicationsystem in which the data rates on specific individual traffic channelsmay be adapted in response to observed channel conditions. For example,the data rate implemented on a particular traffic channel may beselected by changing a Forward Error Correction (FEC) coding rate and/ora selected modulation type depending upon observed conditions in theindividual channels.

In a preferred embodiment, the data rate allocation decisions are madefor a reverse link connection that carries communications between afirst radio station, such as a base station, and a second radio station,such as a field unit. A first parameter that is used in making thisdetermination is a Radio Frequency (RF) path loss. Specifically, pathloss may be determined by sending a message from the first station tothe second station, such as on a paging channel. The message indicates aforward Effective Radiated Power (ERP) of a pilot signal transmitted bythe first station. The second station determines the received signalstrength of this pilot signal, taking into account receive antennagains. The path loss can then be estimated by the second station as thedifference between the forward ERP data value that it received and thedetected received pilot power.

In a case where the first station is a central base station and thesecond station is a field unit, the field unit also preferablydetermines a transmit power level of its local transmit power amplifierwhen transmitting a bandwidth allocation request message on back to thebase station. This transmit power level information is encoded as adigital data word together with the forward path loss information. It ispreferably sent in a message sent from the field unit to the basestation together with an access request message, such as on a dedicatedaccess channel.

Upon receipt of these two pieces of information, the forward path lossestimate as calculated by the field unit and the existing field unitpower amplifier value, the base station can then determine the amount ofexcess power available at the field unit. This excess power differenceis indicative of the amount of dynamic range available in the transmitpower amplifier in the particular field unit. With this information, thebase station can then make a determination as to whether coding rateswhich require a higher dynamic range will be acceptable for use by theparticular field unit. If, for example, a relatively large amount ofexcess power margin appears to be available at the field unit, i.e., insituations where the path loss is relatively low and/or the field unitis transmitting at a relatively low power level, a relatively higherrate code and higher rate modulation may be assigned to the particularfield unit by the base station.

While the detailed description presented herein is in the context of awireless communication system controlling the data rates on a reverselink channel, and wherein such that the paging channel and accesschannel of such a system carry the effective radiated power andestimated path loss information, it should be understood that theinvention may be used in other types of wireless communication systemshaving other channel structures and messaging.

BRIEF DESCRIPTION OF THE DRAWINGS

The foregoing and other objects, features and advantages of theinvention will be apparent from the following more particulardescription of preferred embodiments of the invention, as illustrated inthe accompanying drawings in which like reference characters refer tothe same parts throughout the different views. The drawings are notnecessarily to scale, emphasis instead being placed upon illustratingthe principles of the invention.

FIG. 1 is a block diagram of a wireless communication system in whichthe invention may be employed the control data rates depending uponobserved channel conditions;

FIG. 2 is a more detailed block diagram of a channel encoder showing howchanges in FEC coding rate and modulation type are used to implementdifferent data rates;

FIG. 3 is a circuit diagram for a field unit, transmit power amplifier(PA) Automatic Gain Control (AGC) circuit;

FIG. 4 illustrates the format of an access channel request message thatincludes field unit transmit power and forward path loss information;

FIG. 5 is a diagram for a base station receiver AGC circuit;

FIG. 6 is a diagram illustrating heartbeat channel power calculations;

FIG. 7 illustrates a heartbeat channel Es/No calculation; and

FIG. 8 is a flow chart for how the available data rates are selected.

DETAILED DESCRIPTION 1. System Architecture and Introduction

FIG. 1 is a block diagram illustrating a wireless communication system10 supporting the transmission of data at different rates for particularusers, depending upon observed channel conditions for each user. As inmany wireless communication systems, users compete for wirelessbandwidth allocation. Hence, it is desirable that the wirelesscommunication 10 is optimized for data throughput and, in certainapplications, hi-speed bursts of data throughput. Certain aspects of thepresent invention are based on the recognition that the data ratesassigned to a field unit transmitting over a wireless channel can becontrolled so that minimally interference with other field units usingthe same general wireless airspace is created. Specifically, a radiofrequency (RF) path loss is determined by broadcasting EffectiveRadiated Power (ERP) information from a central base station 20. Aremote field unit 24 receives this ERP information and also determines areceiver signal strength to compute a path loss. The field unit's poweramplifier setting and the result of this path loss calculation are thenreported back to the base station. The base station then, in turn,determines a suitable data rate given the channel conditions.

According to the following description, communication system 10 isdescribed as a wireless data system that uses CDMA coding and timedivision multiplexing to define radio channels. However, it should benoted that the techniques described herein can be applied in othersystem architectures that support shared access. For example, theprinciples of the present invention can be applied to other generalapplications such as telephone connections, computer networkconnections, cable connections, or other physical media to whichallocation of resources such as data channels are granted on anas-needed basis.

As shown, communication system 10 includes a number of Personal Computer(PC) devices 12-1, 12-2, . . . 12-h, . . . 12-m, corresponding fieldunits or terminals 14-1, 14-2, . . . 14-h, . . . 14-m, and associateddirectional antenna devices 16-1, 16-2, . . . 16-h, . . . 16-m.Centrally located equipment includes a base station antenna 18, and acorresponding base station 20 that includes high speed processingcapability. Base station 20 and related infrastructure providesconnections to and from a network gateway 22, network 24 such as theInternet, and network file server 30.

Communication system 10 is preferably a demand access, point tomulti-point wireless communication system such that the PC devices 12can transmit data to and receive data from network server 30 based on alogical connection including bidirectional wireless connectionsimplemented over forward links 40 and reverse links 50. That is, in thepoint to multi-point multiple access wireless communication system 10 asshown, a given base station 20 typically supports communication with anumber of different field units 14 in a manner which is similar to acellular telephone communication network. Accordingly, system 10 canprovide a framework for wireless communication where digital informationis relayed on-demand between multiple mobile cellular users and ahardwired network 24 such as the Internet. PC devices 12 are typicallylaptop computers, handheld units, Internet-enabled cellular telephones,Personal Digital Assistant (PDA)-type computers, digital processors orother end user devices, although almost any type of processing devicecan be used in place of PC devices 12. One or multiple PC devices 12 areeach connected to a respective subscriber unit 14 through a suitablehard wired connection such as an Ethernet-type connection via cable 13.

Each field unit 14 permits its associated PC device 12 to access thenetwork file server 30. In the reverse link 50 direction, that is, fordata traffic transmitted from the PC 12 towards the server 30, the PCdevice 12 transmits information to field unit 14 based on, for example,an Internet Protocol (IP) level network packets. The field unit 14 thenencapsulates the wired framing, i.e., Ethernet framing, with appropriatewireless framing so that data packets can be transmitted over thewireless link of communication system 10. Based on a selected wirelessprotocol, the appropriately formatted wireless data packet then travelsover one of the radio channels that comprise the reverse link 50 throughfield unit antenna 16 to base station antenna 18. At the central basestation location, the base station 20 then extracts the radio linkframed data packets and reformats the packets into an IP format. Thepackets are then routed through gateway 22 and any number or type ofnetworks 24 to an ultimate destination such as a network file server 30.

In one application, information generated by PC device 12 is based on aTCP/IP protocol. Consequently, a PC device 12 has access to digitalinformation such as web pages available on the Internet. It should benoted that other types of digital information can be transmitted overchannels of communication system 10 based on the principles of thepresent invention.

Data can also be transferred from the network file server 30 to PCs 12on forward link 40. In this instance, network data such as IP (InternetProtocol) packets originating at file server 30 travel on network 24through gateway 22 to eventually arrive at base station 20. Aspreviously discussed for reverse link data transmissions, appropriatewireless protocol framing is then added to raw data such as IP packetsfor communication of the packets over wireless forward link 40. Thenewly framed packets then travel via an RF signal through base stationantenna 18 and field unit antenna 16 to the intended target field unit14. An appropriate target field unit 14 decodes the wireless packetprotocol layer, and forwards the packet or data packets to the intendedPC device 12 that performs further processing such as IP layerprocessing.

A given PC device 12 and file server 30 can therefore be viewed as theend points of a logical connection at the IP level. Once a connection isestablished between the base station processor 20 and correspondingfield unit 14, a user at the PC device 12 can then transmit data to andreceive data from file server 30 on an as-needed basis.

The reverse link 50 optimally includes different types of logical and/orphysical radio channels such as an access channel 51, multiple trafficchannels 52-1, . . . 52-m, and a maintenance channel 53. The reverselink access channel 51 is typically used by the subscriber units 14 torequest an allocation of traffic channels by the base station 20. Forexample, traffic channels 52 can be assigned to users on an as-neededbasis. The assigned traffic channels 52 in the reverse link 50 can thencarry payload data from field unit 14 to base station 20.

Notably, a given link between base station 20 and field unit 14 can havemore than one traffic channel 52 assigned to it at a given instant intime. This enables the transfer of information at higher rates.

The maintenance or “heartbeat” channel 53 can be used to carrymaintenance information such as synchronization and power controlmessages to further support transmission of digital information overboth reverse link 50 and forward link 40.

Forward link 40 can include a paging channel 41, which is used by basestation 20 to inform a field unit 14 of general information such as thatone or multiple forward link traffic channels 42 have been allocated toit for forward link data transmissions. Traffic channels 42-1 . . . 42-non the forward link 40 are used to carry payload information from basestation 20 to a corresponding target subscriber unit 14. Maintenancechannel 43 can be used to transmit synchronization and power controlinformation on forward link 40 from base station processor 20 to fieldunits 14. Additionally, a pilot channel 44 can be used to send areference code signal to the field units for synchronization, as well asto broadcast other information.

Traffic channels 42 of the forward link 40 can be shared among multiplesubscriber units 14 based on a Time Division Multiplexing scheme.Specifically, a forward link traffic channel 42 is optionallypartitioned into a predetermined number of periodically repeating timeslots for transmission of data packets from the base station 20 tomultiple subscriber units 14. It should be understood that a givensubscriber unit 14 can, at any instant in time, have multiple time slotsor no time slots assigned to it for use. In certain applications, anentire time-slotted forward or reverse link traffic channel can also beassigned for use by a particular field unit 14 on a continuous basis.

The field units 14 each contain a data processor 15 that performs a datarate management algorithm as described herein below. A data processor 21in the base station 20 also participates in these determinations. So, tothe extent that the data rate determination algorithm is describedbelow, it should be understood that the processors 15 and 21 areperforming the described calculations and tasks.

Radio transceivers in the field units 14 and base station 20 provideaccess to one or more physical communication links such as theillustrated radio channels 40, 50. The physical links are preferablyfurther encoded using known digital multiplexing techniques such as CodeDivision Multiple Access (CDMA) to provide multiple traffic on a givenradio channel or sub-channels. It should be understood that otherwireless communication protocols may also be used to advantage with theinvention.

The communications channels may be implemented by providing multiplecoded sub-channels on a single wide bandwidth CDMA carrier channel suchas having a 1.25 MegaHertz (MHz) bandwidth. The individual channels arethen defined by unique CDMA codes. Alternatively, the multiple channelsmay be provided by single channel physical communication media such asprovided by other wireless communication protocols. What is important isthat the sub-channels may be adversely effected by significant bit errorrates that are unique to each radio channel.

Turning attention now more particularly to the base station 20 and fieldunits 14, they each contain a protocol converter that reformats datafrom a physical layer protocol such as the CDMA protocol in use with themulti-channel radio transceivers and a network layer protocol such asthe TCP/IP protocol providing connections between the computers 12 andthe network server 30.

The protocol converters format data to be transmitted over multiplelogical sub-channels 41, 42, . . . , 45 and 51, 52, . . . , 53 n. Itshould be understood in the following discussion that the connectionsdiscussed herein are bidirectional, and that a “transmitter” may eitherbe a field unit 14 or the base station 20.

FIG. 2 illustrates a more detailed block diagram of a transmitterportion. More particularly, illustrated is the transmitter for theforward link including a protocol converter 45 and multi-channeltransceiver 46 associated with the base station 20. The transmitter inthe field unit 14 is similar.

As can be seen from the diagram, the protocol converter 45 includes asegmenter 60, block coder 61, Forward Error Correction (FEC) coder 62,and symbol modulator 63. Multi-channel transceiver 46 includes ademultiplexer 64 plus a number of channel modulators including at leastone spreading code modulator 65 and channel code modulator 66. It shouldbe understood that there may be a number of spreading code modulators65-1, . . . 65-n, and a corresponding number of channel code modulators66-1, 66-n, depending upon the number of CDMA sub-channels 31-1, . . .31-n, being assigned to a particular forward link connection.

The spreading code modulators 65 preferably apply a pseudonoise (PN)spreading code at a desired chipping rate. The channel code modulators66 further apply a unique orthogonal or PN code to define each CDMAsub-channel. In the preferred embodiment, the coding rate is 1.2288Mega-chips per second with 32 chips per input bit. A summer 67 adds thevarious channel signals together. At this point, additional logicalchannels such as pilot channels and paging channels may be added to thedata channels before all such channels are fed to a Radio Frequency (RF)up converter 68 and power amplifier 69.

The controller 69 provides signals that control the operation of thesegmenter 60, block encoder 61, FEC encoder 62, symbol modulator 63,demultiplexer 64, as well as the allocation of spreading code modulators65 and channel code modulators 66. Specifically, the system may changethe number of bits per block, as applied by the block encoder 61, maychange the particular rate used for error correction coding as appliedby FEC block 62, may change the specific number of bits per symbol, ortier, implemented by the symbol modulator 63, and may change the numberof spreading code modulators 65 and channel code modulators 66 allocatedto a particular connection. It is the flexibility in assigning thesevarious parameters that provides for a number of degrees of freedom inassigning a data rate for specific connections.

The overall information rate can be represented by the expression shownin FIG. 2. This is the ratio of the chip rate divided by the number ofchips per symbol times the number of bits per symbol used in the symbolmodulator 63, number of code words per connection as implemented by thenumber of channel codes implemented by the channel coders 66, and theratio of the information block size divided by the FEC block size asimplemented by the block encoder 61 and FEC encoder 62.

More particularly now with respect to the present invention, certainalgorithms are used by the processors 15 and 21 to determine a suitabledata rate for a given wireless connection. This data rate is determinedfrom observed conditions in the radio channel, which in turn dictates arange of suitable FEC code rate and modulation type, or tier. Asdescribed in the preferred embodiment herein, these algorithms determinea data rate for a reverse link traffic channel that carries data from asubscriber unit 14 towards the base station 20. However, the teachingsherein can be applied to forward link channels or other types ofcommunication systems.

In one implementation of the invention, the reverse link 50 handles arandom access channel 51, two heartbeat or maintenance channels 53 and asingle reverse traffic channel 52. Each user allocated a reverse trafficchannel 52 is given a dynamically allocated tier and code rate based onreceived channel conditions and a reported path loss.

However, in another embodiment, the reverse link 50 handles a randomaccess channel 51, two heartbeat channels 53, and multiple reversetraffic channels 52. Each user allocated a reverse traffic channel 52 isgiven a dynamically allocated tier and code rate based on receivedchannel conditions and the reported path loss. The algorithm in thisinstance keeps track of the total traffic power (interference) allocatedto determine if another user can be added given his possible code ratesand tiers without effecting the existing users.

In another embodiment, the reverse link 50 handles a random accesschannel 51, two heartbeat channels 53 and multiple reverse trafficchannels 52. Each user, allocated a reverse traffic channel is given adynamically allocated tier and code rate based on received channelconditions and the reported path loss. However, the allocation in thiscase is made periodically across all reverse link users who have reversetraffic requests. The allocation in this case attempts to find anoptimum set of code rates and tiers to maximize total reverse capacity.

2. Field Unit Conditions

In order for the base station 20 to make data rate decisions for thereverse link traffic channels 52, certain field unit operatingconditions are determined. First, the path loss between the field unitand the base station is determined. This knowledge is required becausethe multiple tiers and code rates at each tier require different totalreceive power at the base station 20 for adequate operation of theForward Error Correction (FEC) algorithms. In the preferred embodiment,a robust channel structure is selected for the access channel 51, suchas Binary Phase Shift Keyed (BPSK), one-half rate coded, modulation tier2. However, the fact that a user connects to the base successfully usingthe access channel 51 does not give enough information as to whether ornot the user has enough excess power to support higher data rates thatmight be available for the traffic channel(s) 52, such as a ⅘ FEC coderate at 8-QPSK. The field unit 14 therefore, reports two pieces ofinformation to allow the base station to determine the path loss. Theseinclude (a) the forward path loss calculated by the field unit and (b)its existing power amplifier output power. These two values are sent tothe base station 20 in the reverse bandwidth request message transmittedon the access channel.

2.1. Forward Path Loss

The forward path loss is calculated by the field unit as an estimate ofthe forward path loss in [ ] (dB). If the path loss is assumed to bereciprocal and the path loss is known in the forward direction, then itis known in the reverse direction. If the received power is known, thentransmit power at the field unit 14 can be calculated given reverse pathloss. Calculation of the forward path loss should yield a number between40 and 150 dB in most operating environments. The integer portion ofthis loss can therefore be encoded as an 8-bit number representing aloss of between 0 and 255 dB.

The initial power setting for the access channel 51, Field_PA-Pwr, isdetermined by computing an estimate of this forward path loss betweenthe base 20 and field unit 14 and then using this computed number, alongwith a value indicating the received access channel signal roster level,RX_Access_Pwr_Desired. This value passed on the paging channel 41 sothat the field unit 14 can determine the value of Field_PA_Pwr.

The forward path loss calculation by the field unit 14 is as follows:

Fwd_Path_Loss=Fwd_EIRP−Field_RX_Pilot_Pwr+Field_RX_Ant_Gain

Where:

Fwd_EIRP is a number in dBm (i.e. 54 dBm) as sent by the base station 20on the paging channel 41 which represents the forward effectiveisotropic radiated power (EIRP) of the pilot signal 44.

Field_RX_Pilot_Pwr is a number in dBm (i.e. −85 dBm) as detected from afield unit receiver automatic gain control (AGC) circuit whichrepresents the received signal strength of the strongest pilot 41 path.This number will vary in real time as the pilot channel 44 varies inmagnitude.

Field_RX_Ant_Gain is a number in dB (i.e. 6 dB) which represents thegain of the field units 14 receive antenna. This number will most likelybe a constant but may vary by field unit configuration.

An initial set point for Field_PA_Pwr is thus calculated as follows:

Field_PA_Pwr=−RX_Access_Pwr_Desired−Field_TX_Ant_Gain+Fwd_Path_Loss+PA_Step−Duplex_Correction−Offset

Where:

RX_Access_(—) Pwr_Desired is a number in dB ranging from 0 to 63 whichrepresents the desired RX power for the access channel 51 at the base 20with the base receive antenna gain taken into account. As mentionedabove, this number is received over the paging channel 41 and may varydepending on base loading.

Field_TX_Ant_Gain is a number in dB (i.e. 6 dB) which represents thegain of the field units 14 transmit antenna. This number will mostlikely be a constant but may vary by field unit configuration. Use 6 dBfor now.

Fwd_Path_Loss is calculated as described above.

PA_Step is a power step in dB, which is adjusted, based on which accessattempt is being transmitted. For the initial attempt the value is setto 0 dB.

Duplex_Correction is a correction factor in dB related to the path lossdifferences between the transmit (TX) and receive (RX) frequencies. Theduplex frequency split is such that the TX frequency is 80 MHz lowerthan the RX frequency. Since the path loss calculation is made with theRX frequency, the path loss for the transmit path will be less than thatfor the receive path. Use 0.4 dB as an example difference.

Offset is an offset in dB used to reduce the number of bits used toreflect usable dynamic range. This number is typically empiricallydetermined and set for all deployments. Use 80 dB as a representativevalue.

2.2. Field Unit Transmit Power

The field unit transmit power is a measure of transmit power used whenthe channel allocation request message is sent from the field unit tothe base station on the access channel 51. This is the variableField_TX_Pwr outlined above. This number should be encoded as a 6 bitsigned number representing the TX power of the field unit between +32and −31 dBm. The dynamic range of the TX power control on the field unitis greater than 64 dB represented by the 6 bit number, however; thenumber will be used by the base station to determine excess power at thefield unit. The power difference between Tier 3⅓ rate code and Tier 1⅘rate code is much less than 64 dB.

The field unit 14 transmitter requires gain control to set the outputpower and to maintain spectral mask requirements. A block diagram of atypical field unit 14 TX AGC circuit is shown in FIG. 3. The circuitincludes an output power amplifier 69, which receives the encoded andmodulated transmit signal from the transceiver 46 (FIG. 1) through aVariable Gain Amplifier (VGA) 80. An output power level detector 82provides an indicator of the field unit output level to an analog todigital (AD) converter 83. This value is combined with the inputField_PA_Pwr value by a comparator 84 to determine a control value to befed to the VGA 80 through the db to Volts conversion table 85 anddigital to analog (DA) converter 86.

The power detector 82 monitors the PA 69 output power level and feedsthe result back for correction to the input Field_PA_Pwr value.

The dB to Volts table 85 should must be calibrated to control the PAoutput power to within +/−1 dB over a dynamic range of −50 to +26 dBmover temperature.

3. Field Unit Bandwidth Access Request

The field unit access request message sent on the access channel 51includes the forward path loss and field unit transmit powermeasurements as outlined in Sections 2.1 and 2.2 in addition to whatever else the base station 20 may need to allocate one or more trafficchannels to the requesting field unit. FIG. 4 illustrates a format foran access request message 100 sent on the access channel 51. The accessrequest message 100 includes a data field 101, certifying it as anaccess request, and a data field 12 indicating the identity of the fieldunit 14 making the request. Other attributes of the request may beincluded in an attribute field 103. The Field_TX_Pwr 104 value isincluded in field 104, and the calculated FWD_Path_Loss value in datafield 105.

4. Base Station Receive Channel Conditions

Several base station receive channel conditions are also monitored bythe reverse channel capacity management algorithm in the processor 21 todetermine the code rate and tier a field unit 14 can support. Thisrequires two types of measurements, including measurements that affectall reverse channel users, and measurements that are user specific. Theonly measurement that affects all users is the total received power asmeasured by a base station AGC circuit. RMS Delay Spread, received powerper user, and Es/Nt are three user specific measurements which aremaintained for each user who may request reverse traffic channels. Eachof these measurements is described below in greater detail.

4.1. Total Receive Power

One way to estimate reverse link signal to interference ratio (SIR) isto use total received power. Measurement of received power at the basestation is passed to the data rate management algorithm at least onceper epoch.

A base station 20 RX AGC algorithm controls the VGAs in the base stationto maintain a specified headroom and present total received power. Sucha RX AGC circuit for the base station 20 is shown in FIG. 5. It includesthree VGAs 120-1, 120-2, 120-3, an I/Q demodulator 121, analog todigital converters 122, magnitude circuits 123, adder 124, log amp 125,set point adjustment comparator 126, gain block 127, and integrator 128.Measurement of the value Base_RX_Pwr parameter is accomplished bycomputing the sum of the magnitude squared of the I channel and Qchannel (after modulation by QAM block 63 in FIG. 2, the transmittedsignal have both an in-phase (I) and quadrature (Q) component. Blocks121, 122, 123, and 124 accomplish this function. The result is convertedto dB by the log amp 125 and compared to a threshold by comparator 126to set the headroom in the converters. If the math is such that fullscale on the converters is presented by a +1, then the set point is anegative number in dB, which represents the RMS power at the output ofthe converters. AGC_SetPoint should be set to 12 dB.

The error from the set point comparison is scaled by K1 127 and thenintegrated 128. K1 should be set between 0.1 and 0.5. The output of theintegrator 128 contains the gain required by the VGAs 120 to set the RMSoutput at the output of the converters 122 to within 12 dB of fullscale. The actual VGA 120 have both gain and attenuation, so K3 130 isused to shift the gain down to a bipolar number (+/−gain).

VGA Control 134 is used to distribute the required attenuation (loss)across the three variable gain amplifiers 120. The first 15 dB ofattenuation required by the loop should be provided by VGA1 120-1. Thecascade of VGA2 120-2 and VGA3 120-3 should provide the next 30 dB ofattenuation required by the loop. The remaining attenuation should beprovided by VGA1 120-1. This eliminates an output compression issue withthe VGAs 120. The dB to volts tables 135 map dB of attenuation to voltsrequired to drive the VGAs 120. The VGAs 120 are preferablylinear—linear control and not log—linear control.

The total VGA gain is adjusted by K4 134 to produce the total desiredgain. K4 presents the gain between the antenna and VGA input plus theAGC headroom (12 dB) and a 3 dB correction factor (−3 dB) to compensatefor the power measurement at baseband and the real RF power. The lastfactor is necessary because the RMS computation is done at complexbaseband where the crest factor is 3 dB less than that at IF or RF.After the correction by K4 total gain is negated to get the total RXpower in dBm. This result is then filtered and becomes the Base_RX_Pwrvalue in subsequent calculations.

4.2. RMS Delay Spread

The RMS Delay Spread value is a measurement of the relative strength ofthe multi-path present on the reverse link for each field unit 14. Thepreferred manner of taking this measurement is outlined below in section4.5.3. The result of this measurement is a 5-bit number, whichrepresents the pilot multi-path delay spread in ¼ chip increments (0 to8 chips). This measurement is made for both the heartbeat (maintenance)53 and traffic channels 52 for each in-session user. This measurement ispassed to the data rate management algorithm at least once per epochduring traffic and once each heartbeat received.

4.3. Received Channel Power

The received channel power value is a measurement of the received powerfor a single user. This measurement is outlined below in Section 4.5.1.This measurement is made for both the heartbeat (RX_HrtBt_Pwr_Measured)and traffic channels 52 (RX_Trffc_Pwr_Measured). This measurement ispassed to the capacity management algorithm at least once per epochduring traffic and once each heartbeat received.

4.4. Es/Nt

Es/Nt is a measurement of the energy per symbol to total noise densityof each user on the reverse link. This measurement is made only on theheartbeat channels 53 to estimate the channel quality. This measurementis required in order to estimate the interference present on the channel53 given time alignment. Monitoring the power per channel and the totalpower allows computation of the signal to interference ratio (SIR) givenno time alignment. However, with time alignment some amount oforthogonality will be gained on each channel, which needs to be takenadvantage of by the capacity management algorithm. Measurement of theheartbeat Es/Nt allows measurement of Nt which is the interference powerof all other existing users of the reverse link with respect to themeasured user. The measurement is outlined below in Section 4.5.4. Thismeasurement is passed to the capacity management algorithm eachheartbeat period.

4.5 Determining Base Station Parameters

The following describes the processing which is performed on theheartbeat channels (maintenance) 53 channels transmitted by the fieldunit 14.

4.5.1 Base Power Measurement

The heartbeat channel 53 demodulators (diversity paths) compute theheartbeat channel power and time offset by monitoring the power of thethree strongest paths and timing of the single strongest path present ina rake receiver pilot correlation filters (PCF) on a time alignmentsignal or receiver “string”. At the end of a slot time when thedetection is up loaded to the controller the average heartbeat power isalso passed up. The average receive heartbeat channel power may becomputed as shown in FIG. 6.

A PCF peak value is fed from each of three Pilot Correction Filters(PCFs) (not shown) and summed by adder 150. After scaling 151 andconversion to a log scale 152 for dB, a PCF_Hr+Bt_Pwr value indicates areceived heartbeat power level. This value may be adjusted by aBase_RX_Pwr_value and AGC_Setpoint to arrive at theRX_Heartbeat_Pwr_Measured value in dB.

4.5.2 Link Quality Metric

The RX_HrtBt_Pwr_Measured value as output by the power measurementcircuit of FIG. 6 is then manipulated by RX_Ant_Gain and Offset valuesto form a LQM_Metric value which is sent in the LQM slot for thisheartbeat slot if a heartbeat is detected. If the heartbeat signal isnot detected the LQM_Metric is forced down by 1 dB and sent in the LQMslot for this heartbeat slot. The last case covers a condition where afield unit 14 is assigned a heartbeat slot and is not being detected (orthe user is requesting to go active). If this condition happensconsistently across multiple then a new Reverse Traffic AllocationMessage as should be sent to adjust the heartbeat power set point in thefield unit up.

A Link Quality Metric value LQM_Metric is calculated by the data ratedetermination algorithm in the processor 21 as follows:

LQM_Metric=int(abs(RX_HrtBt_Pwr_Measured−RX_Ant_Gain+Offset))

Where:

RX_HrtBt_Pwr_Measured is a number in dBm (i.e. −116 dBm) measured by thebase station per the circuit in FIG. 6.

RX_Ant_Gain is a number in dBi (i.e. 17.5 dBi) indicating the basestation receive antenna gain. It may vary by base station 20 and/or bysector. This number will be determined at the time the base station 20is brought on line and will remain fixed from that point.

Offset is an offset in dB used to reduce the number of bits used toreflect usable dynamic range. This number will be empirically determinedand set for all deployments. Use 80 dB typically.

4.5.3 Base RMS Delay Spread Measurement

The base station measures the RMS delay spread of the heartbeat channel53 and passes this information to the reverse data rate managementalgorithm. The algorithm uses the RMS delay spread to help determine thecode rate and tier that can be supported.

The RMS delay spread for the heartbeat is computed from the path profileaccording to the following equations.

                                      Equation  1 $\begin{matrix}{{MS} = {\frac{\left( {\left( {{PI}_{1}^{2} + {PQ}_{1}^{2}} \right)\mspace{11mu} \bullet \mspace{11mu} k_{1}} \right) + \left( {\left( {{PI}_{2}^{2} + {PQ}_{2}^{2}} \right)\mspace{11mu} \bullet \mspace{11mu} k_{2}} \right) + \left( {\left( {{PI}_{3}^{2} + {PQ}_{3}^{2}} \right)\mspace{11mu} \bullet \mspace{11mu} k_{3}} \right)}{\left( {{PI}_{1}^{2} + {PQ}_{1}^{2}} \right) + \left( {{PI}_{2}^{2} + {PQ}_{2}^{2}} \right) + \left( {{PI}_{3}^{2} + {PQ}_{3}^{2}} \right)}.}} \\{{Mean}\mspace{14mu} {Delay}\mspace{14mu} {Spread}}\end{matrix}$                                       Equation  2$\begin{matrix}{{RMSSpread} = {\sqrt{\frac{\begin{matrix}{{\left( {k_{1} - {MS}} \right)^{2}\mspace{11mu} \bullet \mspace{11mu} \left( {{PI}_{1}^{2} + {PQ}_{1}^{2}} \right)} +} \\{{\left( {k_{2} - {MS}} \right)^{2}\mspace{11mu} \bullet \mspace{11mu} \left( {{PI}_{2}^{2} + {PQ}_{2}^{2}} \right)} + {\left( {k_{3} - {MS}} \right)^{2}\mspace{11mu} \bullet \mspace{11mu} \left( {{PI}_{3}^{2} + {PQ}_{3}^{2}} \right)}}\end{matrix}}{\left( {{PI}_{1}^{2} + {PQ}_{1}^{2}} \right) + \left( {{PI}_{2}^{2} + {PQ}_{2}^{2}} \right) + \left( {{PI}_{3}^{2} + {PQ}_{3}^{2}} \right)}}.}} \\{{RMS}\mspace{14mu} {Delay}\mspace{14mu} {Spread}}\end{matrix}$

Where PI_(x) and PQ_(x) is I and Q of the x^(th) path, k_(x) is the ¼sample position of the x^(th) path. For example; k1 may be 0, k2 may be13 and k3 may be 42. For the base station measurements this calculationwill yield the RMS delay spread in ¼ chip increments. This calculationshould be performed on the demodulators running on the time alignmentstring in the base station 20. This number is preferably made availableto the reverse capacity management once per heartbeat.

4.5.4 Base Es/Nt Measurement

This measurement is made only on the heartbeat channels 53 to estimatethe channel quality. This measurement is required in order to estimatethe interference present on the channel given time alignment. Monitoringthe power per channel and the total power allows computation of thesignal to interference ratio (SIR) given no time alignment. However,with time alignment some amount of orthogonality will be gained on eachchannel, which needs to be taken advantage of by the capacity managementalgorithm. Measurement of the heartbeat Es/Nt allows measurement of Nt,which is the interference power of all other existing users of thereverse link with respect to the measured user.

The Es/Nt calculation is shown graphically in FIG. 7. The complex valuesof the heartbeat demodulator from each rake finger are coherentlycombine 200, 201 and then the I and Q components are squared 202, added203, 204 and the square root taken 205. This calculation yieldsheartbeat magnitude. The heartbeat magnitude is then filtered to yieldthe mean magnitude 200. The mean is then subtracted from the magnitude,squared and then filtered to yield a variance. The mean may bedetermined by a filter 206; the variance by subtractor 210 and squarer211. The mean is then scaled by K2 (0.5) and squared to yield theheartbeat power. The variance is then scaled by K1 (0.5) 212 andfiltered 213 to yield a noise estimate Nt. The scale factors arerequired because of the way the heartbeat channel is de-spread by thedemodulator. The ratio of the power to Nt is computed by 208 and the logcomputed by 216. The value of Es/Nt is passed to the reverse capacitymanagement algorithm once each heartbeat. The reverse capacitymanagement algorithm provides the final averaging or filtering of themeasurement prior to use. The measurement should preferably be made on acoherently combined results of the time alignment string.

5. Reverse Channel Management

The following sections outline the management of the reverse channelsfor each revision of the algorithm. In general, three types of trafficchannels must be managed; the access channel, the heartbeat channels andthe traffic channels. The management of the access and heartbeatchannels requires setting their desired powers. These settings are senton the forward paging channels as a broadcast message for access and asuser specific messages for heartbeat. The traffic channel managementrequires determination of code rate and tier for each user requesting togo active.

5.1 Access Channel Power Setting

This message contains a number in dB ranging from 0 to 63 whichrepresents the desired RX power for the access channel at the base withthe base receive antenna gain taken into account. The calculation ofthis value is as follows:

RX_Access_Pwr_Desired=int(abs(Access_Power−RX_Ant_Gain+Offset))

Where:

Access_Power is a number in dBm (i.e. −116 dBm) controlled by the basestation and will vary by basestation and depend upon input from thereverse capacity management algorithms. This number may change every fewseconds.

RX_Ant_Gain is a number in dBi (i.e. 17.5 dBi) it may vary by basestation and/or by sector. This number will be determined at the time thebase station is brought on line and remain fixed.

Offset is an offset in dB used to reduce the number of bits used toreflect usable dynamic range. This number will be empirically determinedand set for all deployments. Use 80 dB for now.

The management of the access channel requires setting the value forRX_Access_Pwr_Desired transmitted periodically on the forward pagingchannels. The value of RX_Access_Pwr_Desired. is dependent on the valueof an Access_Power parameter which is the power actually measured by thebase station. The value of Access_Power can be computed from theequations

                    Equation  3  Access  Channel  Power$P_{Access} = {I_{Access} + \left( \frac{E_{s}}{N_{t}} \right)_{Access} - {10*\log \; 10\left( {SF}_{Access} \right)}}$

Where: I_(Access) is the interference from other channels and the RFfront end (dBm)

$\left( \frac{E_{s}}{N_{t}} \right)_{Access}$

is the required energy per symbol for the access channel (8 dB)

SF_(Access) is the number of chips per symbol for the access channel(32)

I_(Access) is the interference noise power in dBm from other channelsand the noise generated by the base station front end.

The interference noise power is calculated as shown below.

                Equation  4  Access  Channel  Interference$I_{Access} = {10*\log \; 10\left( {10^{\frac{P_{Traffic}}{10}} + 10^{\frac{P_{Heartbeat}}{10}} + 10^{\frac{P_{Nf}}{10}}} \right)}$${{Where}\text{:}\mspace{14mu} P_{Traffic}} = {I_{Traffic} + \left( \frac{E_{s}}{N_{t}} \right)_{Traffic} - {10*\log \; 10\left( {SF}_{Traffic} \right)}}$$P_{Heartbeat} = {I_{Heartbeat} + \left( \frac{E_{s}}{N_{t}} \right)_{Heartbeat} - {10*\log \; 10\left( {SF}_{Heartbeat} \right)}}$P_(N_(f)) = −174 + 10 * log  10(N_(BW)) + N_(f)$I_{Traffic} = {10*\log \; 10\left( {10^{\frac{P_{Access}}{10}} + 10^{\frac{P_{Heartbeat}}{10}} + 10^{\frac{P_{Nf}}{10}}} \right)}$$I_{Heartbeat} = {10*\log \; 10\left( {10^{\frac{P_{Traffic}}{10}} + 10^{\frac{P_{Access}}{10}} + 10^{\frac{P_{Nf}}{10}}} \right)}$N_(BW) = 1.17 * 10⁶  Hz.N_(f) = 5  dB.

From the above equations it can be seen that computation of the accesschannel power is dependent on the traffic and heartbeat channel powerwhich are intern dependent on the access channel power. If the desired

$\left( \frac{E_{s}}{N_{t}} \right)_{{Access},{Traffic},{Heartbeat}}$

are all known, the set of equations can be reduced to three equations inthree unknowns, if the noise figure of the radio is known. This solutionwill result in an explicit equation for the access power, heartbeatpower and traffic power. As more traffic channels are added the numberof equations and number of unknowns increase accordingly and theexplicit equation for each channel becomes more unwieldy. Another methodfor solving the above set of equations is to solve them recursively. Inthis method the interference powers for each channel is initiallyassumed to be only the noise figure of the radio. The power for eachchannel is then calculated. A new value for the interference power isthen calculated based on the new powers for each channel and the powerfor each channel is then calculated. This process is repeated until thepower calculated for each channel is close (<0.1 dB) between twoiterations and the process is stopped. If the recursion does notconverge then the selected

$\left( \frac{E_{s}}{N_{t}} \right)_{{Access},{Traffic},{Heartbeat}}$

are too high and cannot be supported simultaneously.

5.2 Traffic Channel Data Rate Determination

The determination of the code rate and tier for the reverse link trafficchannels 52 is dynamically determined by the processor 21, based on thereceived channel conditions at the base station. This determination isperformed through the following steps, as also shown on the flow chartof FIG. 8.

Step 200. Based on the measured RMS delay spread from the heartbeatchannel for the user determine the required Es/Nt for each possible coderate and tier.

Step 210. Based on the Es/Nt reported by the heartbeat channel determinethe power required for each of the code rate and tier combinations.

Step 220. Based on the forward path loss reported from the field unitdetermine the power required in the field unit.

Step 230. Given the field unit required power, pick the highest bit ratebased on the tier and code rate supportable with some margin.

Step 240. Send the power level, code rate, and tier in a reverse linksetup message.

Each of these steps is described in more detail below.

5.3.1 Determination of Required Es/Nt (Step 200)

The RMS delay spread for the heartbeat is used to index into a table todetermine an Es/Nt for each code rate tier combination, and for eachpossible delay spread. The table values may be generated in a laboratoryenvironment using a multi-path simulator with RMS delay spreads ofbetween 0.2 and 4 us with a 5 Hz Doppler every 0.2 us. The tables aregenerated such that the set points deliver 1e-6 average Bit Error Rate(BER).

A possible table format is shown below in Table 1. This table is for asystem having nine (9) possible code rate and tier values. In thissituation, three different FEC code rates (⅓, ½ and ⅘) are available,and 3 possible tiers are provided by three different QAM modulationtypes. The path profiles used for this table is an exponentiallyweighted power profile using 6 possible delay spreads in the above RMSdelay spreads. Indexing of the table will result in 9 numbers for eachpossible delay:

$\left( \frac{E_{s}}{N_{t}} \right)_{1/3}^{T\; 1},\left( \frac{E_{s}}{N_{t}} \right)_{1/2}^{T\; 1},\left( \frac{E_{s}}{N_{t}} \right)_{4/5}^{T\; 1},\left( \frac{E_{s}}{N_{t}} \right)_{1/3}^{T\; 2},\left( \frac{E_{s}}{N_{t}} \right)_{1/2}^{T\; 2},\left( \frac{E_{s}}{N_{t}} \right)_{4/5}^{T\; 2},\left( \frac{E_{s}}{N_{t}} \right)_{1/3}^{T\; 3},\left( \frac{E_{s}}{N_{t}} \right)_{1/2}^{T\; 3},\left( \frac{E_{s}}{N_{t}} \right)_{4/5}^{T\; 3}$

and the table therefore has 6×9 or 54 entries.

TABLE 1 Es/Nt Table RMS Delay Spread$\left( \frac{E_{s}}{N_{t}} \right)^{T\; 1}\mspace{14mu} {for}\mspace{14mu} {Tier}\mspace{14mu} 1$$\left( \frac{E_{s}}{N_{t}} \right)^{T\; 2}\mspace{14mu} {for}\mspace{14mu} {Tier}\mspace{14mu} 2$$\left( \frac{E_{s}}{N_{t}} \right)^{T\; 3}\mspace{14mu} {for}\mspace{14mu} {Tier}\mspace{14mu} 3$(us) 1/3 1/2 4/5 1/3 1/2 4/5 1/3 1/2 4/5 0.2 0.4 0.6 0.8 1.0 1.2 1.4 1.61.8 2.0 2.2 2.4 2.6 2.8 3.0 3.2 3.4 3.6 3.8 4.0

5.3.2 Determination of Power Requirements (Step 210)

Based on the nine possible Es/Nt values as determined from the measuredRMS delay spread, the power required at the field unit 14 must then becalculated. The Es/Nt measurement made on the heartbeat channel and themeasured heartbeat power can be used to compute Nt. Once Nt is known,then given each required Es/Nt, the required received power at the basestation can be computed. These calculations are outlined below.

                 Equation  5  Heartbeat  Noise  Calculation$N = {{Pwr}_{Heartbeat} - \left( \frac{E_{s}}{N_{t}} \right)_{Heartbeat} + {10\; {\log (256)}}}$

Where:

Pwr_(Heartbeat) is the measured heartbeat power as outlined above(RX_HrtBt_Pwr_Measured).

$\left( \frac{E_{s}}{N_{t}} \right)_{Heartbeat}$

is the measured energy per symbol to noise density in the heartbeatchannel, as explained above.

10 log(256) is a bandwidth reduction factor due to PN spreading.

The value of N computed above will vary depending on whether or notthere is a user active with reverse channels or an access message waspresent while the measurements are made. Assuming some orthogonalitygain between the traffic and heartbeat channels due to time alignmentthe contribution to N from the traffic channel if present will be smalland would not affect the value of N greatly. If the access channel islightly loaded then the access channel may affect the value of N. Forthis revision of the algorithm enough margin must be included in the setup calculations to handle access channel messaging.

To compute the required power at the base station receiver the noisecalculated in Equation 5 is used with each of the nine possible Es/Nt asfollows:

                Equation  6  Receive  Power  Requirement$C_{\frac{1}{3},\frac{1}{2},\frac{4}{5}}^{{T\; 1},{T\; 2},{T\; 3}} = {N + \left( \frac{E_{s}}{N_{t}} \right)_{\frac{1}{3},\frac{1}{2},\frac{4}{5}}^{{T\; 1},{T\; 2},{T\; 3}} - {10\; {\log \left( {SF}_{{T\; 1},{T\; 2},{T\; 3}} \right)}}}$

Where: SF_(T1)=8, SF_(T2)=32, SF_(T3)=256.

The above calculation results in nine different receive powerrequirements for each tier and code rate combination. These nine powerrequirements are:

-   -   C_(1/3) ^(T1), C_(1/2) ^(T1), C_(4/5) ^(T1), C_(1/3) ^(T2),        C_(1/2) ^(T2), C_(4/5) ^(T2), C_(1/3) ^(T3), C_(1/2) ^(T3),        C_(4/5) ^(T3),

5.3.3. Required Field Unit Power (Step 220)

In order to determine which of the nine power requirements can be met,the required transmit power at the field unit must next be determined.Two values are reported to the base station to allow this calculation;the forward path loss and the field unit PA power used when thebandwidth request message 100 was sent on the access channel. To computethe power available at the base station 20 the following generalequation is used:

P=Field_PA_Power+Field_TX_Ant_Gain−Fwd_Path_Loss+Base_RX_Ant_Gain  Equation7 Base Station Reverse Link Power

Where:

Field_PA_Power is the power set point on the field unit power amplifier.

Field_TX_Ant_Gain is a number in dB (i.e. 6 dB) which represents thegain of the field unit's transmit antenna. This number will most likelybe a constant but may vary by field unit configuration. Use 6 dB fornow.

Fwd_Path_Loss is the path loss in dB between the base station and fieldunit. This number is actually calculated by the field unit and containslosses due to log normal fading and shadowing which are considered to bereciprocal between the forward and reverse links.

Base RX_Ant_Gain is a number in dBi (i.e. 17.5 dBi) indicating basestation antenna gain. It may vary by base station and/or by sector. Thisnumber will be determined at the time the base station is brought online and remains fixed from that point.

Determining the required transmit power at the field unit requires asolution to Equation 7 for each possible code rate and tier. Thecomputation is done in two ways by the base station 20. The firstsolution is use the forward path loss reported by the field unit andassume values for the field transmit antenna gain and base receiveantenna gain. Given these two assumptions, Equation 7 can be manipulatedto give Equation 8 below.

                  Equation  8  Estimated  Field  Transmit  Power${{Field\_ PA}{\_ Power}_{\frac{1}{3},\frac{1}{2},\frac{4}{5}}^{{T\; 1},{T\; 2},{T\; 3}}} = {C_{\frac{1}{3},\frac{1}{2},\frac{4}{5}}^{{T\; 1},{T\; 2},{T\; 3}} - {{Field\_ TX}{\_ Ant}{\_ Gain}} + {{Fwd\_ Path}{\_ Loss}} - {{Base\_ RX}{\_ Ant}{\_ Gain}}}$

Where

$C_{\frac{1}{3},\frac{1}{2},\frac{4}{5}}^{{T\; 1},{T\; 2},{T\; 3}}$

is the received power requirement at the base station for each code rateand tier combination. The above calculation yields nine (9) possiblefield unit power settings.

The other solution to Equation 7 is to use the PA setting reported inthe bandwidth request message on the reverse link to determine the sumof the field transmit antenna gain, forward path loss, and base receiveantenna gain. This calculation is shown below in Equation 9.

P_(Measured)=PA_(TX)+Field_TX_Ant_Gain−Fwd_Path_Loss+Base_RX_Ant_Gain  Equation9

Where:

P_(Measured) is the measured receive power on the access channel whenthe bandwidth request message was received.

PA_(TX) is the field unit transmit power when the bandwidth requestmessage was sent from the field unit.

Equation 9 can be manipulated to yield the components of Equation 7which are not known and then substituted into Equation 8 to yieldEquation 10.

                  Equation  10  Estimated  Field  Transmit  PowerP_(Measured) − PA_(TX) = Field_TX_Ant_Gain − Fwd_Path_Loss + Base_RX_Ant_Gain$\mspace{20mu} {{{Field\_ PA}{\_ Power}_{\frac{1}{3},\frac{1}{2},\frac{4}{5}}^{{T\; 1},{T\; 2},{T\; 3}}} = {C_{\frac{1}{3},\frac{1}{2},\frac{4}{5}}^{{T\; 1},{T\; 2},{T\; 3}} - P_{Measured} + {PA}_{TX}}}$

The above calculation also yields nine (9) possible field unit powersettings.

Both calculations are subject to error. In the first solution the fieldtransmit antenna gain and base receive antenna gains are not preciselyknown. However, if the field transmit antenna is reciprocal with thereceive gain (or nearly so) and the base receive antenna gain isreciprocal with the transmit antenna gain then most of the error fallsout (because of the way forward path loss is calculated and the powerset points for the traffic sent the in the reverse link setup message).In the second solution the antenna gains are lumped with the path lossand are not a factor. However, the accuracy of the measurement of theaccess channel power is degraded due to the possibility of collisionsoccurring on the channel, which introduces error. Making an error incomputing the necessary power at the field unit means the channel isconfigured at too high a tier/code rate and an acceptable FER cannot besupported because the field unit is in a power limit condition, orpossibly the field unit is operating at a tier/code rate below thatwhich it is capable of.

The above two solutions yield 18 possible field PA power requirements,two for each tier/code rate combination. In order to prevent the case oftoo high a tier/code rate from being selected, the highest field PApower setting for each tier/code rate is selected from the two methods.Due to the nature of the calculation all nine settings will come fromeither one solution method or the other.

5.3.4 Tier/Code Rate/Power Selection (Step 230)

Given the nine possible field PA settings calculated above, thetier/code rate/and receive power at the base station must then beselected. Each of the of the possible field PA settings is compared tothe maximum field PA power to determine which are within the capabilityof the field unit. The maximum field PA power is currently +26 dBm.Ultimately this may vary by field unit and would be reported in theprotocol revision etc. sent in the initial connection to the basestation or stored with user data at the WIF. Any field power requirementabove (+26 dBm—Link Margin) should be discarded since it is beyond thecapability of the field unit. Link Margin is some number of dBs used tocompensate for Raleigh fading, errors in the above calculations, andaccess messaging. For this revision of the algorithm Link Margin can beprogrammable and initially set to 3 dB.

Of the remaining tier code rate combinations the combination yieldingthe highest bit rate should be selected. One possible bit rate for eachtier and code rate with a 6% pilot symbol insertion factor is shown inTable 2:

TABLE 2 Nine Possible Reverse Bit Rates (kb/s) Code Rate Tier 1/3 1/24/5 1 80.6 132.9 224.5 2 20.2 33.2 56.1 3 5.0 8.3 14.0

With the highest bit rate selected from the above table, the tier andcode rate are then known. Given the tier and code rate combination, thereceived power at the base station is now also known based on theresults of Equation 6. This value is Traffic_Pwr is discussed above.

5.3.5 Reverse Traffic Channel Allocation Message (Step 240)

This message is formulated including information as to selected tier andcode rate, and forwarded to the field unit 14 so that it may properlyset its power level.

While this invention has been particularly shown and described withreferences to preferred embodiments thereof, it will be understood bythose skilled in the art that various changes in form and details may bemade therein without departing from the scope of the inventionencompassed by the appended claims.

What is claimed is:
 1. A wireless field unit comprising: a transceiveroperatively coupled to a processor, the transceiver and the processorconfigured to receive a plurality of forward link assignment messagesfor a plurality of time slots for a plurality of forward linktransmissions; wherein each forward link assignment message includes anindication of a modulation and a code rate associated with a respectiveforward link transmission; the transceiver and the processor furtherconfigured to receive at least one of the forward link transmissions inat least one time slot, wherein each received forward link transmissionis received at the respective indicated modulation and code rate; thetransceiver and the processor further configured to receive a pluralityof reverse link assignment messages for a plurality of time slots for aplurality of reverse link transmissions; wherein each reverse linkassignment message includes an indication of a modulation and a coderate associated with a respective reverse link transmission; and thetransceiver and the processor configured to transmit at least one of thereverse link transmissions in at least one time slot, wherein eachtransmitted reverse link transmission is transmitted at the respectiveindicated modulation and code rate.
 2. The wireless field unit of claim1, wherein the transceiver and the processor are further configured totransmit an indication of an amount of excess power that the field unitis capable of using; and wherein the transceiver and the processor arefurther configured, in response to the transmitted indication of theamount of excess power, to receive a reverse link assignment message. 3.The wireless field unit of claim 1, wherein the transceiver and theprocessor are further configured to receive power setting informationfor a first reverse link channel and a second reverse link channel. 4.The wireless field unit of claim 3, wherein the first reverse linkchannel is assigned in response to at least one received reverse linkassignment message.
 5. A method comprising: receiving, by a wirelessfield unit, a plurality of forward link assignment messages for aplurality of time slots for a plurality of forward link transmissions;wherein each forward link assignment message includes an indication of amodulation and a code rate associated with a respective forward linktransmission; receiving, by the wireless field unit, at least one of theforward link transmissions in at least one time slot, wherein eachreceived forward link transmission is received at the respectiveindicated modulation and code rate; receiving, by the wireless fieldunit, a plurality of reverse link assignment messages for a plurality oftime slots for a plurality of reverse link transmissions; wherein eachreverse link assignment message includes an indication of a modulationand a code rate associated with a respective reverse link transmission;and transmitting, by the wireless field unit, at least one of thereverse link transmissions in at least one time slot, wherein eachtransmitted reverse link transmission is transmitted at the respectiveindicated modulation and code rate.
 6. The method of claim 5 furthercomprising transmitting, by the field unit, an indication of an amountof excess power that the field unit is capable of using; and, inresponse to the transmitted indication of the amount of excess power,receiving, by the wireless field unit, a reverse link assignmentmessage.
 7. The method of claim 5 further comprising receiving, by thewireless field unit, power setting information for a first reverse linkchannel and a second reverse link channel.
 8. The method of claim 7wherein the first reverse link channel is assigned to the wireless fieldunit in response to at least one received reverse link assignmentmessage.
 9. A base station comprising: a transceiver operatively coupledto a processor, the transceiver and the processor configured to transmita plurality of forward link assignment messages for a plurality of timeslots for a plurality of forward link transmissions; wherein eachforward link assignment message includes an indication of a modulationand a code rate associated with a respective forward link transmission;the transceiver and the processor further configured to transmit atleast one of the forward link transmissions in at least one time slot,wherein each transmitted forward link transmission is transmitted at therespective indicated modulation and code rate; the transceiver and theprocessor further configured to transmit a plurality of reverse linkassignment messages for a plurality of time slots for a plurality ofreverse link transmissions; wherein each reverse link assignment messageincludes an indication of a modulation and a code rate associated with arespective reverse link transmission; and a transceiver and theprocessor configured to receive at least one of the reverse linktransmissions in at least one time slot, wherein each received reverselink transmission is received at the respective indicated modulation andcode rate.
 10. The base station of claim 9 wherein the transceiver andthe processor are further configured to receive an indication of anamount of excess power that a field unit is capable of using; andwherein the transceiver and the processor are further configured, inresponse to the transmitted indication of the amount of excess power, totransmit a reverse link assignment message.
 11. The base station ofclaim 9 wherein the transceiver and the processor are further configuredto transmit power setting information for a first reverse link channeland a second reverse link channel.
 12. The base station of claim 11wherein the first reverse link channel is assigned in response to atleast one transmitted reverse link assignment message.